Programmably Reversible Resistive Device Cells Using CMOS Logic Processes

ABSTRACT

Junction diodes fabricated in standard CMOS logic processes can be used as program selectors for reversible resistive devices, such as PCM, RRAM, CBRAM, or other memory cells. The reversible resistive devices have a reversible resistive element coupled to a diode. The diode can be constructed by P+ and N+ active regions on an N well as the P and N terminals of the diode. By applying a voltage or a current between a reversible resistive element and the N terminal of a diode, the reversible resistive device can be programmed into different states based on magnitude, duration, voltage-limit, or current-limit in a reversible manner. The P+ active region of the diode can be isolated from the N+ active region in the N well by using dummy MOS gate, SBL, or STI/LOCOS isolations.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No. 13/026,840, filed on Feb. 14, 2011 and entitled “Programmably Reversible Resistive Device Cells using CMOS Logic Processes,” which is hereby incorporated herein by reference, and which in turn claims priority benefit of: (i) U.S. Provisional Patent Application No. 61/375,653, filed on Aug. 20, 2010 and entitled “Circuit and System of Using Junction Diode As Program Selector for Resistive Devices in CMOS Logic Processes,” which is hereby incorporated herein by reference; and (ii) U.S. Provisional Patent Application No. 61/375,660, filed on Aug. 20, 2010 and entitled “Circuit and System of Using Polysilicon Diode As Program Selector for Resistive Devices in CMOS Logic Processes,” which is hereby incorporated herein by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to programmable memory devices, such as programmable resistive devices for use in memory arrays.

2. Description of the Related Art

A programmable resistive device is generally referred to a device's resistance states that may change after means of programming. Resistance states can also be determined by resistance values. For example, a resistive device can be a One-Time Programmable (OTP) device, such as electrical fuse, and the programming means can apply a high voltage to induce a high current to flow through the OTP element. When a high current flows through an OTP element by turning on a program selector, the OTP element can be programmed, or burned into a high or low resistance state (depending on either fuse or anti-fuse).

An electrical fuse is a common OTP which is a programmable resistive device that can be constructed from a segment of interconnect, such as polysilicon, silicided polysilicon, silicide, metal, metal alloy, or some combination thereof. The metal can be aluminum, copper, or other transition metals. One of the most commonly used electrical fuses is a CMOS gate, fabricated in silicided polysilicon, used as interconnect. The electrical fuse can also be one or more contacts or vias instead of a segment of interconnect. A high current may blow the contact(s) or via(s) into a very high resistance state. The electrical fuse can be an anti-fuse, where a high voltage makes the resistance lower, instead of higher. The anti-fuse can consist of one or more contacts or vias with an insulator in between. The anti-fuse can also be a CMOS gate coupled to a CMOS body with a thin gate oxide as insulator.

The programmable resistive device can be a reversible resistive device that can be programmed into a digital logic value “0” or “1” repetitively and reversibly. The programmable resistive device can be fabricated from phase change material, such as Germanium (Ge), Antimony (Sb), and Tellurium (Te) with composition Ge₂Sb₂Te₅ (GST-225) or GeSbTe-like materials including compositions of Indium (In), Tin (Sn), or Selenium (Se). The phase change material can be programmed into a high resistance amorphous state or a low resistance crystalline state by applying a short and high voltage pulse or a long and low voltage pulse, respectively. The reversible resistive device can be a Resistive RAM (RRAM) with cells fabricated from metal oxides between electrodes, such as Pt/NiO/Pt, TiN/TiOx/HfO2/TiN, TiN/ZnO/Pt. The resistance states can be changed reversibly and determined by polarity, magnitude, duration, or voltage/current-limit of pulse(s) to generate or annihilate conductive filaments. Another programmable resistive device similar to RRAM is a Conductive Bridge RAM (CBRAM) that is based on electro-chemical deposition and removal of metal ions in a thin solid-state electrolyte film. The electrodes can be an oxidizable anode and an inert cathode and the electrolyte can be Ag- or Cu-doped chalcogenide glass such as GeSe or GeS, etc. The resistance states can be changed reversibly and determined by polarity, magnitude, duration, or voltage/current-limit of pulse(s) to generate or annihilate conductive bridges. The programmable resistive device can be an MRAM (Magnetic RAM) with cells fabricated from magnetic multi-layer stacks that construct a Magnetic Tunnel Junction (MTJ). In a Spin Transfer Torque MRAM (STT-MRAM) the direction of currents applied to an MTJ determines parallel or anti-parallel states, and hence low or high resistance states.

A conventional programmable resistive memory cell is shown in FIG. 1. The cell 10 consists of a resistive element 11 and an NMOS program selector 12. The resistive element 11 is coupled to the drain of the NMOS 12 at one end, and to a positive voltage V+ at the other end. The gate of the NMOS 12 is coupled to a select signal (Sel), and the source is coupled to a negative voltage V−. When a high voltage is applied to V+ and a low voltage to V−, the resistive device 10 can be programmed by raising the select signal (Sel) to turn on the NMOS 12. One of the most common resistive elements is a silicided polysilicon, the same material and fabricated at the same time as a MOS gate. The size of the NMOS 12, as program selector, needs to be large enough to deliver the required program current for a few microseconds. The program current for a silicided polysilicon is normally between a few milliamps for a fuse with width of 40 nm to about 20 mA for a fuse with width about 0.6 um. As a result, the cell size of an electrical fuse using silicided polysilicon tends to be very large.

Another conventional programmable resistive device 20 for Phase Change Memory (PCM) is shown in FIG. 2( a). The PCM cell 20 has a phase change film 21 and a bipolar transistor 22 as program selector with P+ emitter 23, N-base 27, and P-sub collector 25. The phase change film 21 is coupled to the emitter 23 of the bipolar transistor 22 at one end, and to a positive voltage V+ at the other. The N-type base 27 of bipolar transistor 22 is coupled to a negative voltage V−. The collector 25 is coupled to ground. By applying a proper voltage between V+ and V− for a proper duration of time, the phase change film 21 can be programmed into high or low resistance states, depending on voltage and duration. Conventionally, to program a phase-change memory to a high resistance state (or reset state) requires about 3V for 50 ns and consumes about 300 uA of current, or to program a phase-change memory to a low resistance state (or set state) requires about 2V for 300 ns and consumes about 100 uA of current.

FIG. 2( b) shows a cross section of a conventional bipolar transistor 22. The bipolar transistor 22 includes a P+ active region 23, a shallow N well 24, an N+ active region 27, a P-type substrate 25, and a Shallow Trench Isolation (STI) 26 for device isolation. The P+ active region 23 and N+ active region 27 couple to the N well 24 are the P and N terminals of the emitter-base diode of the bipolar transistor 22, while the P-type substrate 25 is the collector of the bipolar transistor 22. This cell configuration requires an N well 24 be shallower than the STI 26 to properly isolate cells from each other and needs 3-4 more masking steps over the standard CMOS logic processes which makes it more costly to fabricate.

Another programmable resistive device 20′ for Phase Change Memory (PCM) is shown in FIG. 2( c). The PCM cell 20′ has a phase change film 21′ and a diode 22′. The phase change film 21′ is coupled between an anode of the diode 22′ and a positive voltage V+. A cathode of the diode 22′ is coupled to a negative voltage V−. By applying a proper voltage between V+ and V− for a proper duration of time, the phase change film 21′ can be programmed into high or low resistance states, depending on voltage and duration. As an example of use of a diode as program selector for each PCM cell as shown in FIG. 2( c), see Kwang-Jin Lee et al., “A 90 nm 1.8V 512 Mb Diode-Switch PRAM with 266 MB/s Read Throughput,” International Solid-State Circuit Conference, 2007, pp. 472-273. Though this technology can reduce the PCM cell size to only 6.8 F² (F stands for feature size), the diode requires very complicated process steps, such as Selective Epitaxial Growth (SEG), to fabricate, which would be very costly for embedded PCM applications.

FIGS. 3( a) and 3(b) show several embodiments of an electrical fuse element 80 and 84, respectively, fabricated from an interconnect. The interconnect serves as a particular type of resistive element. The resistive element has three parts: anode, cathode, and body. The anode and cathode provide contacts for the resistive element to be connected to other parts of circuits so that a current can flow from the anode to cathode through the body. The body width determines the current density and hence the electro-migration threshold for a program current. FIG. 3( a) shows a conventional electrical fuse element 80 with an anode 81, a cathode 82, and a body 83. This embodiment has a large symmetrical anode and cathode. FIG. 3( b) shows another conventional electrical fuse element 84 with an anode 85, a cathode 86, and a body 87. This embodiment has an asymmetrical shape with a large anode and a small cathode to enhance the electro-migration effect based on polarity and reservoir effects. The polarity effect means that the electro-migration always starts from the cathode. The reservoir effect means that a smaller cathode makes electro-migration easier because the smaller area has lesser ions to replenish voids when the electro-migration occurs. The fuse elements 80, 84 in FIGS. 3( a) and 3(b) are relatively large structures which makes them unsuitable for some applications.

FIGS. 4( a) and 4(b) show programming a conventional MRAM cell 210 into parallel (or state 0) and anti-parallel (or state 1) by current directions. The MRAM cell 210 consists of a Magnetic Tunnel Junction (MTJ) 211 and an NMOS program selector 218. The MTJ 211 has multiple layers of ferromagnetic or anti-ferromagnetic stacks with metal oxide, such as Al₂O₃ or MgO, as an insulator in between. The MTJ 211 includes a free layer stack 212 on top and a fixed layer stack 213 underneath. By applying a proper current to the MTJ 211 with the program selector CMOS 218 turned on, the free layer stack 212 can be aligned into parallel or anti-parallel to the fixed layer stack 213 depending on the current flowing into or out of the fixed layer stack 213, respectively. Thus, the magnetic states can be programmed and the resultant states can be determined by resistance values, lower resistance for parallel and higher resistance for anti-parallel states. The resistances in state 0 or 1 are about 5KΩ or 10KΩ, respectively, and the program currents are about +/−100-200 μA. One example of programming an MRAM cell is described in T. Kawahara, “2 Mb Spin-Transfer Torque RAM with Bit-by-Bit Bidirectional Current Write and Parallelizing-Direction Current Read,” International Solid-State Circuit Conference, 2007, pp. 480-481.

SUMMARY OF THE INVENTION

Embodiments of programmable resistive device cells using junction diodes as program selectors are disclosed. The programmable resistive devices can be fabricated using standard CMOS logic processes to reduce cell size and cost.

In one embodiment, junction diodes fabricated in standard CMOS logic processes can be used as program selectors for reversible resistive devices, such as PCRAM, RRAM, CBRAM, or other memory cells. The reversible resistive devices have a reversible resistive element coupled to a diode. The diode can be constructed by P+ and N+ active regions on an N well as the P and N terminals of the diode. By applying a voltage or a current between a reversible resistive element and the N-terminal of a diode, the reversible resistive device can be programmed into different states based on magnitude, duration, voltage-limit, or current-limit in a reversible manner. The P+ active region of the diode can be isolated from the N+ active region in the N-well by using dummy MOS gate, SBL, or STI/LOCOS isolations.

The invention can be implemented in numerous ways, including as a method, system, device, or apparatus (including graphical user interface and computer readable medium). Several embodiments of the invention are discussed below.

As a reversible resistive memory, one embodiment can, for example, include at least a plurality of reversible resistive cells. At least one of the reversible resistive cells can include a reversible resistive film coupled to a first supply voltage line, and a diode including at least a first active region and a second active region. The first active region can have a first type of dopant and the second region can have a second type of dopant. The first active region can provide a first terminal of the diode, the second active region can provide a second terminal of the diode, and both the first and second active regions can reside in a common well. The first active region can be coupled to the reversible resistive film, and the second active region can be coupled to a second supply voltage line. The active regions can be fabricated from sources or drains of CMOS devices, and the common well can be fabricated from a CMOS well. The reversible resistive film can be configured to be programmable by applying voltages to the first and the second supply voltage lines to change the resistance into a different logic state in a reversible manner.

As a phase-change memory, one embodiment can, for example, include at least a plurality of phase-change cells. At least one of the phase-change cells including a phase-change film coupled to a first supply voltage line, and a diode including at least a first active region and a second active region. The first active region can have a first type of dopant and the second region can have a second type of dopant. The first active region can provide a first terminal of the diode, the second active region can provide a second terminal of the diode, and both the first and second active regions can reside in a common well. The first active region can be coupled to the phase-change film, and the second active region can be coupled to a second supply voltage line. The active regions can be fabricated from sources or drains of CMOS devices, and the common well can be fabricated from a CMOS well. The phase-change film can be configured to be programmable by applying voltages to the first and the second supply voltage lines to thereby change the resistance into a different logic state in a reversible manner.

As an electronics system, one embodiment can, for example, include at least a processor, and a reversible resistive memory operatively connected to the processor. The reversible resistive memory can include at least a plurality of reversible resistive cells. At least one of the cells including at least a reversible resistive film coupled to a first supply voltage line, and a diode including at least a first active region and a second active region. The first active region can have a first type of dopant and the second region can have a second type of dopant. The first active region can provide a first terminal of the diode, the second active region can provide a second terminal of the diode, both the first and second active regions can reside in a common well. The first active region can be coupled to the reversible resistive film, and the second active region can be coupled to a second supply voltage line. The active regions can be fabricated from sources or drains of CMOS devices, and the common well being fabricated from a CMOS well. The reversible resistive film is configured to be programmed by applying voltages to the first and the second supply voltage lines to thereby change the resistance into a different logic state in a reversible manner.

As a method for providing a reversible resistive memory, one embodiment can, for example, include at least providing a plurality of reversible resistive memory cells. At least one of the reversible memory cells can include at least a reversible resistive film coupled to a first supply voltage line, and a diode including at least a first active region and a second active region. The first active region can have a first type of dopant and the second region can have a second type of dopant. The first active region can provide a first terminal of the diode, the second active region can provide a second terminal of the diode, and both the first and second active regions residing in a common well. The first active region coupled to the reversible resistive film, and the second active region coupled to a second supply voltage line. The active regions can be fabricated from sources or drains of CMOS devices, and the common well being fabricated from a CMOS wells. The embodiment of the method can also include programming at least one of the reversible memory cells into a different logic state by applying voltages to the first and the second supply voltage lines to thereby change the resistance of the reversible resistive film.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention will be readily understood by the following detailed descriptions in conjunction with the accompanying drawings, wherein like reference numerals designate like structural elements, and in which:

FIG. 1 shows a conventional programmable resistive memory cell.

FIG. 2( a) shows another conventional programmable resistive device for Phase Change Memory (PCM) using bipolar transistor as program selector.

FIG. 2( b) shows a cross section of a conventional Phase Change Memory (PCM) using bipolar transistor as program selector.

FIG. 2( c) shows another conventional Phase Change Memory (PCM) cell using diode as program selector.

FIGS. 3( a) and 3(b) show several embodiments of an electrical fuse element, respectively, fabricated from an interconnect.

FIGS. 4( a) and 4(b) show programming a conventional MRAM cell into parallel (or state 0) and anti-parallel (or state 1) by current directions.

FIG. 5( a) shows a block diagram of a memory cell using a junction diode according to the invention.

FIG. 5( b) shows a cross section of a junction diode as program selector with STI isolation according to one embodiment.

FIG. 5( c) shows a cross section of a junction diode as program selector with CMOS gate isolation according to one embodiment.

FIG. 5( d) shows a cross section of a junction diode as program selector with SBL isolation according to one embodiment.

FIG. 6( a) shows a cross section of a junction diode as program selector with dummy CMOS gate isolation in SOI technologies according to one embodiment.

FIG. 6( b) shows a cross section of a junction diode as program selector with dummy CMOS gate isolation in FINFET technologies according to one embodiment.

FIG. 7( a) shows an electrical fuse element according to one embodiment.

FIG. 7( b) shows a top view of an electrical fuse coupled to a junction diode with STI isolation in four sides.

FIG. 7( c) shows a top view of an electrical fuse coupled to a junction diode with STI isolation in two sides and dummy CMOS isolation in another two sides.

FIG. 7( d) shows a top view of an electrical fuse coupled to a junction diode with dummy CMOS isolation in four sides.

FIG. 7( e) shows a top view of an electrical fuse coupled to a junction diode with Silicide Block Layer isolation in four sides.

FIG. 7( f) shows an abutted contact coupled between a resistive element, P terminal of a junction diode, and metal in a single contact.

FIG. 8( a) shows a top view of a metal fuse coupled to a junction diode with dummy CMOS gate isolation.

FIG. 8( b) shows a top view of a metal fuse coupled to a junction diode with 4 cells sharing one N well contact in each side.

FIG. 8( c) shows a top view of a via1 fuse coupled to a junction diode with 4 cells sharing one N well contact in each side.

FIG. 8( d) shows a top view of a two-dimensional array of via1 fuses using P+/N well diodes.

FIG. 9( a) shows a cross section of a programmable resistive device cell using phase-change material as a resistive element, with buffer metals and a P+/N well junction diode, according to one embodiment.

FIG. 9( b) shows a top view of a PCM cell using a P+/N well junction diode as program selector in accordance with one embodiment.

FIG. 10 shows one embodiment of an MRAM cell using diodes as program selectors in accordance with one embodiment.

FIG. 11( a) shows a top view of an MRAM cell with an MTJ as a resistive element and with P+/N well diodes as program selectors in standard CMOS processes in accordance with one embodiment.

FIG. 11( b) shows another top view of an MRAM cell with an MTJ as a resistive element and with P+/N well diodes as program selectors in a shallow well CMOS process in accordance with another embodiment.

FIG. 12( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using junction diodes as program selectors and the condition to program the upper-right cell into 1 in accordance with one embodiment.

FIG. 12( b) shows alternative conditions to program the upper-right cell into 1 in a 2×2 MRAM array in accordance with one embodiment.

FIG. 13( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using junction diodes as program selectors and the condition to program the upper-right cell into 0 in accordance with one embodiment.

FIG. 13( b) shows alternative conditions to program the upper-right cell into 0 in a 2×2 MRAM array in accordance with one embodiment.

FIGS. 14( a) and 14(b) show one embodiment of programming 1 and 0 into the upper-right cell, respectively, in a two-terminal 2×2 MRAM cell array in accordance with one embodiment.

FIG. 15 shows a portion of a programmable resistive memory constructed by an array of n-row by (m+1)-column non-MRAM cells and n wordline drivers in accordance with one embodiment.

FIG. 16( a) shows a portion of a programmable resistive memory constructed by an array of 3-terminal MRAM cells according to one embodiment.

FIG. 16( b) shows another embodiment of constructing a portion of MRAM memory with 2-terminal MRAM cells.

FIGS. 17( a), 17(b), and 17(c) show three other embodiments of constructing reference cells for differential sensing.

FIG. 18( a) shows a schematic of a wordline driver circuit according to one embodiment.

FIG. 18( b) shows a schematic of a bitline circuit according to one embodiment.

FIG. 18( c) shows a portion of memory with an internal power supply VDDP coupled to an external supply VDDPP and a core logic supply VDD through power selectors.

FIG. 19( a) shows one embodiment of a schematic of a pre-amplifier according to one embodiment.

FIG. 19( b) shows one embodiment of a schematic of an amplifier according to one embodiment.

FIG. 19( c) shows a timing diagram of the pre-amplifier and the amplifier in FIGS. 19( a) and 19(b), respectively.

FIG. 20( a) shows another embodiment of a pre-amplifier, similar to the pre-amplifier in FIG. 18( a).

FIG. 20( b) shows level shifters according to one embodiment.

FIG. 20( c) shows another embodiment of an amplifier with current-mirror loads.

FIG. 21( a) depicts a method of programming a programmable resistive memory in a flow chart according to one embodiment.

FIG. 21( b) depicts a method of reading a programmable resistive memory in a flow chart according to one embodiment.

FIG. 22 shows a processor system according to one embodiment.

DETAILED DESCRIPTION OF THE INVENTION

Embodiments disclosed herein use a P+/N well junction diode as program selector for a programmable resistive device. The diode can comprise P+ and N+ active regions on an N well. Since the P+ and N+ active regions and N well are readily available in standard CMOS logic processes, these devices can be formed in an efficient and cost effective manner. There are no additional masks or process steps to save costs. The programmable resistive device can also be included within an electronic system.

FIG. 5( a) shows a block diagram of a memory cell 30 using a junction diode according to one embodiment. In particular, the memory cell 30 includes a resistive element 30 a and a junction diode 30 b. The resistive element 30 a can be coupled between an anode of the junction diode 30 b and a positive voltage V+. A cathode of the junction diode 30 b can be coupled to a negative voltage V−. In one implementation, the memory cell 30 can be a fuse cell with the resistive element 30 a operating as an electrical fuse. The junction diode 30 b can serve as a program selector. The junction diode can be constructed from a P+/N well in standard CMOS processes using a P-type substrate. The P+ and N+ active regions serve as the anode and cathode of the diode are the sources or drains of CMOS devices. The N well is a CMOS well to house PMOS devices. Alternatively, the junction diode can be constructed from N+/P well in triple-well or CMOS processes using an N-type substrate. The coupling of the resistive element 30 a and the junction diode 30 b between the supply voltages V+ and V− can be interchanged. By applying a proper voltage between V+ and V− for a proper duration of time, the resistive element 30 a can be programmed into high or low resistance states, depending on voltage and duration, thereby programming the memory cell 30 to store a data value (e.g., bit of data). The P+ and N+ active regions of the diode can be isolated by using a dummy CMOS gate, Shallow Trench Isolation (STI) or Local Oxidation (LOCOS), or Silicide Block Layer (SBL).

Electrical fuse cell can be used as an example to illustrate the key concepts according to one embodiment. FIG. 5( b) shows a cross section of a diode 32 using a P+/N well diode as program selector with Shallow Trench Isolation (STI) isolation in a programmable resistive device. P+ active region 33 and N+ active region 37, constituting the P and N terminals of the diode 32 respectively, are sources or drains of PMOS and NMOS in standard CMOS logic processes. The N+ active region 37 is coupled to an N well 34, which houses PMOS in standard CMOS logic processes. P-substrate 35 is a P-type silicon substrate. STI 36 isolates active regions for different devices. A resistive element (not shown in FIG. 5( b)), such as electrical fuse, can be coupled to the P+ region 33 at one end and to a high voltage supply V+ at the other end. To program this programmable resistive device, a high voltage is applied to V+, and a low voltage or ground is applied to the N+ region 37. As a result, a high current flows through the fuse element and the diode 32 to program the resistive device accordingly.

FIG. 5( c) shows a cross section of another embodiment of a junction diode 32′ as program selector with dummy CMOS gate isolation. Shallow Trench Isolation (STI) 36′ provides isolation among active regions. An active region 31′ is defined between STI 36′, where the N+ and P+ active regions 37′ and 33′ are further defined by a combination of a dummy CMOS gate 39′, P+ implant layer 38′, and N+ implant (the complement of the P+ implant 38′), respectively, to constitute the N and P terminals of the diode 32′. The diode 32′ is fabricated as a PMOS-like device with 37′, 39′, 33′, and 34′ as source, gate, drain, and N well, except that the source 37′ is covered by an N+ implant, rather than a P+ implant 38′. The dummy MOS gate 39′, preferably biased at a fixed voltage, only serves for isolation between P+ active region 33′ and N+ active region 37′ during fabrication. The N+ active 37′ is coupled to an N well 34′, which houses PMOS in standard CMOS logic processes. P-substrate 35′ is a P-type silicon substrate. A resistive element (not shown in FIG. 5( c)), such as electrical fuse, can be coupled to the P+ region 33′ at one end and to a high voltage supply V+ at the other end. To program this programmable resistive device, a high voltage is applied to V+, and a low voltage or ground is applied to the N+ active region 37′. As a result, a high current flows through the fuse element and the diode 32′ to program the resistive device accordingly. This embodiment is desirable for isolation for small size and low resistance.

FIG. 5( d) shows a cross section of another embodiment of a junction diode 32″ as program selector with Silicide Block Layer (SBL) isolation. FIG. 5( d) is similar to 5(c), except that the dummy CMOS gate 39′ in FIG. 5( c) is replaced by SBL 39″ in FIG. 5( d) to block a silicide grown on the top of active region 31″. Without a dummy MOS gate or a SBL, the N+ and P+ active regions would be undesirably electrically shorted by a silicide on the surface of the active region 31″.

FIG. 6( a) shows a cross section of another embodiment of a junction diode 32″ as a program selector in Silicon-On-Insulator (SOI) technologies. In SOI technologies, the substrate 35″ is an insulator such as SiO₂ or similar material with a thin layer of silicon grown on top. All NMOS and PMOS are in silicon wells isolated by SiO₂ or similar material to each other and to the substrate 35″. One-piece active region 31″ is divided into an N+ active region 37″, P+ active region 33″, and body 34″ by a combination of a dummy CMOS gate 39″, P+ implant 38″, and N+ implant (the complement of P+ implant 38″). Consequently, the N+ active region 37″ and P+ active region 33″ constitute the N and P terminals of the junction diode 32″. The N+ active region 37″ and P+ active region 33″ can be the same as sources or drains of NMOS and PMOS devices, respectively, in standard CMOS processes. Similarly, the dummy CMOS gate 39″ can be the same CMOS gate fabricated in standard CMOS processes. The dummy MOS gate 39″, which can be biased at a fixed voltage, only serves for isolation between P+ active region 33″ and N+ active region 37″ during fabrication. The N+ active region 37″ can be coupled to a low voltage supply V− and to an N well 34″ that houses PMOS in standard CMOS SOI processes. A resistive element (not shown in FIG. 6( a)), such as an electrical fuse, can be coupled to the P+ active region 33″ at one end and to a high voltage supply V+ at the other end. To program the electrical fuse cell, a high and low voltages are applied to V+ and V−, respectively, to conduct a high current flowing through the fuse element and the junction diode 32″ to program the resistive device accordingly. Other embodiments of isolations in CMOS bulk technologies, such as STI, dummy MOS gate, or SBL in one to four (1-4) or any sides, can be readily applied to CMOS SOI technologies accordingly.

FIG. 6( b) shows a cross section of another embodiment of a junction diode 45 as a program selector in FinFET technologies. FinFET refers to a fin-based, multigate transistor. FinFET technologies are similar to the conventional CMOS except that thin and tall silicon islands can be raised above the silicon substrate to serve as the bulks of CMOS devices. The bulks are divided into source, drain, and channel regions by polysilicon or non-aluminum metal gates like in the conventional CMOS. The primary difference is that the MOS devices are raised above the substrate so that channel widths are the height of the islands, though the direction of current flow is still in parallel to the surface. In an example of FinFET technology shown in FIG. 6( b), the silicon substrate 35 is an epitaxial layer built on top of an insulator like SOI or other high resistivity silicon substrate. The silicon substrate 35 can then be etched into several tall rectangular islands 31-1, 31-2, and 31-3. With proper gate oxide grown, the islands 31-1, 31-2, and 31-3 can be patterned with MOS gates 39-1, 39-2, and 39-3, respectively, to cover both sides of raised islands 31-1, 31-2, and 31-3 and to define source and drain regions. The source and drain regions formed at the islands 31-1, 31-2, and 31-3 are then filled with silicon, such as fill 40-1 and 40-2, so that the combined source or drain areas are large enough to allow contacts. The fill 40-1 and 40-2 areas in FIG. 6( b) are for illustrative purpose to reveal the cross section and can, for example, be filled up to the surface of the islands 31-1, 31-2, and 31-3. In this embodiment, active regions 33-1,2,3 and 37-1,2,3 are covered by a P+ implant 38 and N+ implant (the complement of P+ implant 38), respectively, rather than all covered by P+ implant 38 as PMOS in the conventional FinFET, to constitute the P and N terminals of the junction diode 45. The N+ active region 37-1,2,3 is coupled to a low voltage supply V−. A resistive element (not shown in FIG. 6( b)), such as an electrical fuse, is coupled to the P+ active region 33-1,2,3 at one end and to a high voltage supply V+ at the other end. To program the electrical fuse, high and low voltages are applied between V+ and V−, respectively, to conduct a high current flowing through the resistive element and the junction diode 45 to program the resistive device accordingly. Other embodiments of isolations in CMOS bulk technologies, such as STI, dummy MOS gate or SBL, can be readily applied to FinFET technologies accordingly.

FIG. 7( a) shows a top view of an electrical fuse element 88 according to one embodiment. The electrical fuse element 88 can, for example, by used as the resistive element 31 a illustrated in FIGS. 5( a). The electrical fuse element 88 includes an anode 89, a cathode 90, and a body 91. In this embodiment, the electrical fuse element 88 is a bar shape with a small anode 89 and cathode 90 to reduce area. The anode 89 and cathode 90 may protrude from the body 91 to make contacts. The contact number can be one (1) for both the anode 89 and the cathode 90 so that the area can be very small. However, the contact area for anode 89 is often made larger so that the anode 89 can resist electro-migration more than the cathode 90. The fuse body 91 can have about 1-5 squares, namely, the length to width ratio is about 1-to-5, to optimize cell area and program current. The fuse element 88 has a P+ implant 92 covering half of the body 91 and the cathode 90, while an N+ implant over the rest of area. This embodiment makes the fuse element 88 behave like a reverse biased diode to increase resistance after being programmed, when silicide on top is depleted by electro-migration, ion diffusion, silicide decomposition, and other effects.

The above scheme can be realized for those fuse elements consisting of polysilicon, silicided polysilicon, or other CMOS gate material so that P+ and N+ implants can create a diode. For example, if a metal-gate CMOS has a sandwich structure of polysilicon between metal alloy layers, the metal alloy layers may be blocked by masks generated from layout database to create a diode in the fuse elements.

FIGS. 7( b), 7(c), 7(d), 7(e), and 7(f) show top views of P+/N well diodes constructed with different embodiments of isolation and fuse elements. Without isolation, P+ and N+ active regions would be shorted together by silicide grown on top. The isolation can be provided by STI, dummy CMOS gate, SBL, or some combination thereof from one to four (1-4) or any sides. The P+ and N+ active regions that act as P and N terminals of the diodes are sources or drains of CMOS devices. Both the P+ and N+ active regions reside in an N well, which is the same N well that can be used to house PMOS in standard CMOS processes. The N+ active region of the diodes in multiple cells can be shared, though for simplicity FIGS. 7( b)-7(f) show only one N+ active region for one P+ active region.

FIG. 7( b) shows a top view of one embodiment of a P+/N well diode 40 in an electrical fuse cell having active regions 43 and 44 with STI 49 isolation in four sides. A fuse element 42 is coupled to the active region 43 through a metal 46. The active regions 43 and 44 are covered by a P+ implant 47 and N+ implant (the complement of P+ implant 47), respectively, to constitute the P and N terminals of the diode 40. The active regions 43 and 44 of the diode 40 reside in an N well 45, the same N well can be used to house PMOS in standard CMOS processes. In this embodiment, the P+ active region 43 and N+ active region 44 are surrounded by an STI 49 in four (4) sides. Since the STI 49 is much deeper than either the N+ or P+ active region, the resistance of the diode 40 between the P+ active region 43 and N+ active region 44 is high.

FIG. 7( c) shows a top view of another embodiment of a P+/N well diode 50 in an electrical fuse cell having active regions 53 and 54 with an STI 59 isolation in two sides and a dummy MOS gate 58 in another two sides. One-piece active region 51 with two STI slots 59 in the right and left is divided into a peripheral 54 and a central 53 regions by two MOS gates 58 on top and bottom. The central active region 53 is covered by a P+ implant 57, while the peripheral active region 54 is covered by an N+ implant layer (the complement of the P+ implant), which constitute the P and N terminals of the diode 50. The active region 51 resides in an N well 55, the same N well can be used to house PMOS in standard CMOS processes. A fuse element 52 is coupled to the P+ active region 53. The dummy MOS gate 58 is preferably biased to a fixed voltage. In this embodiment, the P+ active region 53 and N+ active region 54 are surrounded by STI 59 in left and right sides and the dummy MOS gate 58 on top and bottom. The isolation provided by the dummy MOS gate 58 can provide lower resistance than the STI isolation, because the space between the P+ active region 53 and N+ active region 54 may be narrower and there is no oxide to block the current path underneath the silicon surface.

FIG. 7( d) shows a top view of yet another embodiment of P+/N well diode 60 in an electrical fuse cell with dummy MOS gate 68 providing isolation in four sides. One-piece active region 61 is divided into a center active region 63 and a peripheral active region 64 by a ring-shape MOS gate 68. The center active region 63 is covered by a P+ implant 67 and the peripheral active region 64 is covered by an N+ implant (the complement of the P+ implant 67), respectively, to constitute the P and N terminals of the diode 60. The active region 61 resides in an N well, the same N well can be used to house PMOS in standard CMOS processes. A fuse element 62 is coupled to the P+ active region 63 through a metal 66. The dummy MOS gate 68, which can be biased at a fixed voltage, provides isolation between P+ active region 63 and N+ active region 64 regions on four sides. This embodiment offers low resistance between P and N terminals of the diode 60.

FIG. 7( e) shows a top view of yet another embodiment of a P+/N well diode 60′ in an electrical fuse cell having active regions 63′ and 64′ with Silicide Block Layer (SBL) 68′ providing isolation in four sides. One-piece active region 61′ is divided into a center active region 63′ and a peripheral active region 64′ by an SBL ring 68′. The center active region 63′ and the peripheral active region 64′ are covered by a P+ implant 67′ and an N+ implant (the complement of P+ implant 67′), respectively, to constitute the P and N terminals of the diode 60′. The boundaries between the P+ implant 67′ and N+ implants are about in the middle of the SBL ring 68′. The active region 61′ resides in an N well 65′. A fuse element 62′ is coupled to the P+ active region 63′ through a metal 66′. The SBL ring 68′ blocks silicide formation on the top of the active regions between P+ active region 63′ and N+ active region 64′. In this embodiment, the P+ active region 63′ and N+ active region 64′ are isolated in four sides by P/N junctions. This embodiment has low resistance between the P and N terminals of the diode 60′, though the SBL may be wider than a MOS gate. In another embodiment, there is a space between the P+ implant 67′ and the N+ implant that is covered by the SBL ring 68′.

FIG. 7( f) shows a top view of another embodiment of a P+/N well diode 70 in an electrical fuse cell with an abutted contact. Active regions 73 and 74, which are isolated by an STI 79, are covered by a P+ implant 77 and an N+ implant (the complement of the P+ implant 77), respectively, to constitute the P and N terminals of the diode 70. Both of the active regions 73 and 74 reside in an N well 75, the same N well can be used to house PMOS in standard CMOS processes. A fuse element 72 is coupled to the P+ active region 73 through a metal 76 in a single contact 71. This contact 71 is quite different from the contacts in FIG. 7( b), (c), (d), and (e) where a contact can be used to connect a fuse element with a metal and then another contact is used to connect the metal with a P+ active region. By connecting a fuse element directly to an active region through a metal in a single contact, the cell area can be reduced substantially. This embodiment for a fuse element can be constructed by a CMOS gate, including polysilicon, silicided polysilicon, or non-aluminum metal CMOS gate, that allows an abutted contact.

In general, a polysilicon or silicide polysilicon fuse is more commonly used as an electrical fuse because of its lower program current than metal or contact/via fuses. However, a metal fuse has some advantages such as smaller size and wide resistance ratio after being programmed. Metal as a fuse element allows making contacts directly to a P+ active region thus eliminating one additional contact as compared to using a polysilicon fuse. In advanced CMOS technologies with feature size less than 65 nm, the program voltage for metal fuses can be lower than 3.3V, which makes metal fuse a viable solution.

FIG. 8( a) shows a top view of P+/N well diode 60″ having a metal1 fuse with dummy CMOS gate isolation. One-piece active region 61 is divided into a center active region 63 and a peripheral active region 64 by a ring-shape MOS gate 68. The center active region 63 is covered by a P+ implant 67 and the peripheral active region 64 is covered by an N+ implant (the complement of the P+ implant 67), respectively, to constitute the P and N terminals of the diode 60″. The active region 61 resides in an N well 65, the same N well can be used to house PMOS in standard CMOS processes. A metal1 fuse element 62″ is coupled to the P+ region 63 directly. The ring-shape MOS gate 68, which provides dummy CMOS gate isolation, can be biased at a fixed voltage, and can provide isolation between P+ active 63 and N+ active 64 regions in four sides. In one embodiment, the length to width ratio of a metal fuse is about 1-5.

The size of the metal fuse cell in FIG. 8( a) can be further reduced, if the turn-on resistance of the diode is not crucial. FIG. 8( b) shows a top view of a row of metal fuse cells 60′″ having four metal fuse cells that share one N well contact in each side in accordance with one embodiment. Metal1 fuse 69 has an anode 62′, a metal1 body 66′, and a cathode coupled to an active region 64′ covered by a P+ implant 67′ that acts as the P terminal of a diode. The active region 61′ resides in an N well 65′. Another active region 63′ covered by an N+ implant (complement of P+ implant 67′) acts as N terminal of the diode. Four diodes are isolated by STI 68′ and share one N+ active region 63′ each side. The N+ active regions 63′ are connected by a metal2 running horizontally, and the anode of the diode is connected by a metal3 running vertically. If metal1 is intended to be programmed, other types of metals in the conduction path should be wider. Similarly, more contacts and vias should be put in the conduction path to resist programming. It should be noted metal1 as a metal fuse in FIG. 8( b) is for illustrative purposes, those skilled in the art understand that the above description can be applied to any metals, such as metal2, metal3, or metal4 in other embodiments. Similarly, those skilled in the art understand that the isolation, metal scheme, and the number of cells sharing one N+ active may vary in other embodiments.

Contact or via fuses may become more viable for advanced CMOS technologies with feature size less than 65 nm, because small contact/via size makes program current rather low. FIG. 8( c) shows a top view of a row of four via1 fuse cells 70 sharing N-type well contacts 73 a and 73 b in accordance with one embodiment. Vial fuse cell 79 has a via1 79 a coupled to a metal1 76 and a metal2 72. Metal2 72 is coupled to a metal3 through via2 89 running vertically as a bitline. Metal1 76 is coupled to an active region 74 covered by a P+ implant 77 that acts as the P terminal of a diode 71. Active regions 73 a and 73 b covered by an N+ implant (complement of P+ implant 77) serves as the N terminal of the diode 71 in via1 fuse cell 79. Moreover, the active regions 73 a and 73 b serve as the common N terminal of the diodes in the four-fuse cell 70. They are further coupled to a metal4 running horizontally as a wordline. The active regions 74, 73 a, and 73 b reside in the same N well 75. Four diodes in via1 fuse cells 70 have STI 78 isolation between each other. If via1 is intended to be programmed, more contacts and more other kinds of vias should be put in the conduction path. And metals in the conduction path should be wider and contain large contact/via enclosures to resist programming. Vial as a via fuse in FIG. 8( c) is for illustrative purpose, those skilled in the art understand that the above description can be applied to any kinds of contacts or vias, such as via2, via3, or via4, etc. Similarly, those skilled in the art understand that the isolation, metal scheme, and the number of cells sharing one N+ active may vary in other embodiments.

FIG. 8( d) shows a top view of an array of 4×5 via1 fuses with dummy CMOS gate isolation in accordance with one embodiment. The one-row via fuse shown in FIG. 8( c) can be extended into a two-dimensional array 90 as shown in FIG. 8( d). The array 90 has four rows of active regions 91, each residing in a separate N well, and five columns of via fuse cells 96, isolated by dummy CMOS gates 92 between active regions. Each via fuse cell 96 has one contact 99 on an active region covered by a P+ implant 94 that acts as the P terminal of a diode, which is further coupled to a metal2 bitline running vertically. Active regions in two sides of the array 90 are covered by N+ implant 97 to serve as the N terminals of the diodes in the same row, which is further coupled to metal3 as wordlines running horizontally. To program a via fuse, select and apply voltages to the desired wordline and bitline to conduct a current from metal2 bitline, via1, metal1, contact, P+ active, N+ active, to metal3 wordline. To ensure only via1 is programmed, metals can be made wider and the numbers of other types of vias or contact can be more than one. To simplify the drawing, metal1-via1-metal2 connection can be referred to FIG. 8( c) and, therefore, is not shown in each cell in FIG. 8( d). Those skilled in the art understand that various types of contact or vias can be used as resistive elements and the metal schemes may change in other embodiments. Similarly, the number of cells in rows and columns, the numbers of rows or columns in an array, and the numbers of cells between N+ active may vary in other embodiments.

FIG. 9( a) shows a cross section of a programmable resistive device cell 40 using phase-change material as a resistive element 42, with buffer metals 41 and 43, and a P+/N well diode 32, according to one embodiment. The P+/N well diode 32 has a P+ active region 33 and N+ active region 37 on an N well 34 as P and N terminals. The isolation between the P+ active region 33 and N+ active region 37 is an STI 36. The P+ active region 33 of the diode 32 is coupled to a lower metal 41 as a buffer layer through a contact plug 40-1. The lower metal 41 is then coupled to a thin film of phase change material 42 (e.g., GST film). An upper metal 43 also couples to the thin film of the phase-change material 42 through a contact plug 40-2. The upper metal 43 is coupled to another metal 44 to act as a bitline (BL) through a plug 40-3. The phase-change film 42 can have a chemical composition of Gemanimum (Ge), Antimony (Sb), and Tellurium (Te), such as Ge_(x)Sb_(y)Te_(z) (x, y and z are any arbitrary numbers), or as one example Ge₂Sb₂Te₅ (GST-225). The GST film can be doped with at least one or more of Indium (In), Tin (Sn), or Selenium (Se) to enhance performance. The phase-change cell structure can be substantially planar, which means the phase-change film 42 has an area that is larger than the film contact area coupled to the program selector, or the height from the surface of the silicon substrate to the phase-change film 42 is much smaller than the dimensions of the film parallel to silicon substrate. In this embodiment, the active area of phase-change film 42 is much larger than the contact area so that the programming characteristics can be more uniform and reproducible. The phase-change film 42 is not a vertical structure and does not sit on top of a tall contact, which can be more suitable for embedded phase-change memory applications, especially when the diode 32 (i.e., junction diode) is used as program selector to make the cell size very small. For those skilled in the art understand that the structure and fabrication processes may vary and that the structures of phase-change film (e.g., GST film) and buffer metals described above are for illustrative purpose.

FIG. 9( b) shows a top view of a PCM cell using a junction diode as program selector having a cell boundary 80 in accordance with one embodiment. The PCM cell has a P+/N well diode and a phase-change material 85, which can be a GST film. The P+/N well diode has active regions 83 and 81 covered by a P+ implant 86 and an N+ implant (complement of P+ implant 86), respectively, to serve as the anode and cathode. Both active regions 81 and 83 reside on an N well 84, the same N well can be used to house PMOS in standard CMOS processes. The anode is coupled to the phase-change material 85 through a metal1 82. The phase-change material 85 is further coupled to a metal3 bitline (BL) 88 running vertically. The cathode of the P+/N well diode (i.e., active region 81) is connected by a metal2 wordline (WL) 87 running horizontally. By applying a proper voltage between the bitline 88 and the wordline 87 for a suitable duration, the phase-change material 85 can be programmed into a 0 or 1 state accordingly. Since programming the PCM cell is based on raising the temperature rather than electro-migration as with an electrical fuse, the phase-change film (e.g., GST film) can be symmetrical in area for both anode and cathode. Those skilled in the art understand that the phase-change film, structure, layout style, and metal schemes may vary in other embodiments.

Programming a phase-change memory (PCM), such as a phase-change film, depends on the physical properties of the phase-change film, such as glass transition and melting temperatures. To reset, the phase-change film needs to be heated up beyond the melting temperature and then quenched. To set, the phase-change film needs to be heated up between melting and glass transition temperatures and then annealed. A typical PCM film has glass transition temperature of about 200° C. and melting temperature of about 600° C. These temperatures determine the operation temperature of a PCM memory because the resistance state may change after staying in a particular temperature for a long time. However, most applications require retaining data for 10 years for the operation temperature from 0 to 85° C. or even from −40 to 125° C. To maintain cell stability over the device's lifetime and over such a wide temperature range, periodic reading and then writing back data into the same cells can be performed. The refresh period can be quite long, such as longer than a second (e.g., minutes, hours, days, weeks, or even months). The refresh mechanism can be generated inside the memory or triggered from outside the memory. The long refresh period to maintain cell stability can also be applied to other emerging memories such as RRAM, CBRAM, and MRAM, etc.

FIG. 10 shows one embodiment of an MRAM cell 310 using diodes 317 and 318 as program selectors in accordance with one embodiment. The MRAM cell 310 in FIG. 10 is a three-terminal MRAM cell. The MRAM cell 310 has an MTJ 311, including a free layer stack 312, a fixed layer stack 313, and a dielectric film in between, and the two diodes 317 and 318. The free layer stack 312 is coupled to a supply voltage V, and coupled to the fixed layer stack 313 through a metal oxide such as Al₂O₃ or MgO. The diode 317 has the N terminal coupled to the fixed layer stack 313 and the P terminal coupled to V+ for programming a 1. The diode 318 has the P terminal coupled to the fixed layer stack 313 and the N terminal coupled to V− for programming a 0. If V+ voltage is higher than V, a current flows from V+ to V to program the MTJ 311 into state 1. Similarly, if V− voltage is lower than V, a current flows from V to V− to program the MTJ 311 into state 0. During programming, the other diode is supposedly cutoff. For reading, V+ and V− can be both set to 0V and the resistance between node V and V+/V− can be sensed to determine whether the MTJ 311 is in state 0 or 1.

FIG. 11( a) shows a cross section of one embodiment of an MRAM cell 310 with MTJ 311 and junction diodes 317 and 318 as program selectors in accordance with one embodiment. MTJ 311 has a free layer stack 312 on top and a fixed layer stack 313 underneath with a dielectric in between to constitute a magnetic tunneling junction. Diode 317 is used to program 1 and diode 318 is used to program 0. Diodes 317 and 318 have P+ and N+ active regions on N wells 321 and 320, respectively, the same N wells to house PMOS in standard CMOS processes. Diode 317 has a P+ active region 315 and N+ active region 314 to constitute the P and N terminals of the program-1 diode 317. Similarly, diode 318 has a P+ active 316 and N+ active 319 to constitute the P and N terminals of the program-0 diode 318. FIG. 11( a) shows STI 330 isolation for the P and N terminals of diodes 317 and 318. For those skilled in the art understand that different isolation schemes, such as dummy MOS gate or SBL, can alternatively be applied.

The free stacks 312 of the MTJ 311 can be coupled to a supply voltage V, while the N terminal of the diode 318 can be coupled to a supply voltage V− and the P terminal of the diode 317 can be coupled to another supply voltage V+. Programming a 1 in FIG. 11( a) can be achieved by applying a high voltage, i.e., 2V to V+ and V−, while keeping V at ground, or 0V. To program a 1, a current flows from diode 317 through the MTJ 311 while the diode 318 is cutoff. Similarly, programming a 0 can be achieved by applying a high voltage to V, i.e., 2V, and keeping V+ and V− at ground. In this case. a current flows from MTJ 311 through diode 318 while the diode 317 is cutoff.

FIG. 11( b) shows a cross section of another embodiment of an MRAM cell 310′ with MTJ 311′ and junction diodes 317′ and 318′ as program selectors in accordance with one embodiment. MTJ 311′ has a free layer stack 312′ on top and a fixed layer stack 313′ underneath with a dielectric in between to constitute a magnetic tunneling junction. Diode 317′ is used to program 1 and diode 318′ is used to program 0. Diodes 317′ and 318′ have P+ and N+ active regions on N wells 321′ and 320′, respectively, which are fabricated by shallow N wells with additional process steps. Though more process steps are needed, the cell size can be smaller. Diode 317′ has P+ active region 315′ and N+ active region 314′ to constitute the P and N terminals of the program-1 diode 317′. Similarly, diode 318′ has P+ active 316′ and N+ active 319′ to constitute the P and N terminals of the program-0 diode 318′. STI 330′ isolates different active regions.

The free stacks 312′ of the MTJ 311′ can be coupled to a supply voltage V, while the N terminal of the diode 318′ can be coupled to a supply voltage V− and the P terminal of the diode 317′ is coupled to another supply voltage V+. Programming a 1 in FIG. 11( b) can be achieved by applying a high voltage, i.e., 2V to V+ and V−, while keeping V at ground, or 0V. To program a 1, a current will flow from diode 317′ through the MTJ 311′ while the diode 318′ is cutoff. Similarly, programming 0 can be achieved by applying a high voltage to V, i.e., 2V, and keeping V+ and V− at ground. In this case, a current will flow from MTJ 311′ through diode 318′ while the diode 317′ is cutoff.

FIG. 12( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using junction diodes 317 and 318 as program selectors and the condition to program 1 in a cell in accordance with one embodiment. Cells 310-00, 310-01, 310-10, and 310-11 are organized as a two-dimensional array. The cell 310-00 has a MTJ 311-00, a program-1 diode 317-00, and a program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of the program-1 diode 317-00 and to the P terminal of the program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The other cells 310-01, 310-10, and 310-11 are similarly coupled. The voltage Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0P and WL0N, respectively. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1P and WL1N, respectively. To program a 1 into the cell 310-01, WL0P is set high and BL1 is set low, while setting the other BL and WLs at proper voltages as shown in FIG. 12( a) to disable the other program-1 and program-0 diodes. The bold line in FIG. 12( a) shows the direction of current flow.

FIG. 12( b) shows alternative program-1 conditions for the cell 310-01 in a 2×2 MRAM array in accordance with one embodiment. For example, to program a 1 into cell 310-01, set BL1 and WL0P to low and high, respectively. If BL0 is set to high in condition 1, the WL0N and WL1N can be either high or floating, and WL1P can be either low or floating. The high and low voltages of an MRAM in today's technologies are about 2-3V for high voltage and 0 for low voltage, respectively. If BL0 is floating in condition 2, WL0N and WL1N can be high, low, or floating, and WL1P can be either low or floating. In a practical implementation, the floating nodes are usually coupled to very weak devices to a fixed voltage to prevent leakage. One embodiment of the program-1 condition is shown in FIG. 12( a) without any nodes floating.

FIG. 13( a) shows one embodiment of a three-terminal 2×2 MRAM cell array with MTJ 311 and junction diodes 317 and 318 as program selectors and the condition to program 0 in a cell in accordance with one embodiment. The cells 310-00, 310-01, 310-10, and 310-11 are organized as a two-dimensional array. The cell 310-00 has a MTJ 311-00, a program-1 diode 317-00, and a program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of program-1 diode 317-00 and to the P terminal of program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The other cells 310-01, 310-10, and 310-11 are similarly coupled. The voltage Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0P and WL0N, respectively. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1P and WL1N, respectively. To program a 0 into the cell 310-01, WL0N is set low and BL1 is set high, while setting the other BL and WLs at proper voltages as shown in FIG. 13( a) to disable the other program-1 and program-0 diodes. The bold line in FIG. 13( a) shows the direction of current flow.

FIG. 13( b) shows alternative program-0 conditions for the cell 310-01 in a 2×2 MRAM array in accordance with one embodiment. For example, to program a 0 into cell 310-01, set BL1 and WL0N to high and low, respectively. If BL0 is set to low in condition 1, the WL0P and WL1P can be either low or floating, and WL1N can be either high or floating. The high and low voltages of an MRAM in today's technologies are about 2-3V for high voltage and 0 for low voltage, respectively. If BL0 is floating in condition 2, WL0P and WL1P can be high, low, or floating, and WL1N can be either high or floating. In a practical implementation, the floating nodes are usually coupled to very weak devices to a fixed voltage to prevent leakage. One embodiment of the program-0 condition is as shown in FIG. 13( a) without any nodes floating.

The cells in 2×2 MRAM arrays in FIGS. 12( a), 12(b), 13(a) and 13(b) are three-terminal cells, namely, cells with V, V+, and V− nodes. However, if the program voltage VDDP is less than twice a diode's threshold voltage Vd, i.e. VDDP<2*Vd, the V+ and V− nodes of the same cell can be connected together as a two-terminal cell. Since Vd is about 0.6-0.7V at room temperature, this two-terminal cell works if the program high voltage is less than 1.2V and low voltage is 0V. This is a common voltage configuration of MRAM arrays for advanced CMOS technologies that has supply voltage of about 1.0V. FIGS. 14( a) and 14(b) show schematics for programming a 1 and 0, respectively, in a two-terminal 2×2 MRAM array.

FIGS. 14( a) and 14(b) show one embodiment of programming 1 and 0, respectively, in a two-terminal 2×2 MRAM cell array in accordance with one embodiment. The cells 310-00, 310-01, 310-10, and 310-11 are organized in a two-dimensional array. The cell 310-00 has the MTJ 311-00, the program-1 diode 317-00, and the program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of program-1 diode 317-00 and the P terminal of program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The voltages V+ and V− are connected together in the cell level if VDDP<2*Vd can be met. The other cells 310-01, 310-10 and 310-11 are similarly coupled. The voltages Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1.

To program a 1 into the cell 310-01, WL0 is set high and BL1 is set low, while setting the other BL and WLs at proper voltages as shown in FIG. 14( a) to disable other program-1 and program-0 diodes. The bold line in FIG. 14( a) shows the direction of current flow. To program a 0 into the cell 310-01, WL0 is set low and BL1 is set high, while setting the other BL and WLs at proper voltages as shown in FIG. 14( b) to disable the other program-1 and program-0 diodes. The bold line in FIG. 14( b) shows the direction of current flow.

The embodiments of constructing MRAM cells in a 2×2 array as shown in FIGS. 12( a)-14(b) are for illustrative purposes. Those skilled in the art understand that the number of cells, rows, or columns in a memory can be constructed arbitrarily and rows and columns are interchangeable.

The programmable resistive devices can be used to construct a memory in accordance with one embodiment. FIG. 15 shows a portion of a programmable resistive memory 100 constructed by an array 101 of n-row by (m+1)-column non-MRAM cells 110 and n wordline drivers 150-i, where i=0, 1, . . . , n−1, in accordance with one embodiment. The memory array 101 has m normal columns and one reference column for one shared sense amplifier 140 for differential sensing. Each of the memory cells 110 has a resistive element 111 coupled to the P terminal of a diode 112 as program selector and to a bitline BLj 170-j (j=0, 1, . . . m−1) or reference bitline BLR0 175-0 for those of the memory cells 110 in the same column. The N terminal of the diode 112 is coupled to a wordline WLBi 152-i through a local wordline LWLBi 154-i, where i=0, 1, . . . , n−1, for those of the memory cells 110 in the same row. Each wordline WLBi is coupled to at least one local wordline LWLBi, where i=0, 1, . . . , n−1. The LWLBi 154-i is generally constructed by a high resistivity material, such as N well or polysilicon, to connect cells, and then coupled to the WLBi (e.g., a low-resistivity metal WLBi) through conductive contacts or vias, buffers, or post-decoders 172-i, where i=0, 1, . . . , n−1. Buffers or post-decoders 172-i may be needed when using diodes as program selectors because there are currents flowing through the WLBi, especially when one WLBi drives multiple cells for program or read simultaneously in other embodiments. The wordline WLBi is driven by the wordline driver 150-i with a supply voltage vddi that can be switched between different voltages for program and read. Each BLj 170-j or BLR0 175-0 is coupled to a supply voltage VDDP through a Y-write pass gate 120-j or 125 for programming, where each BLj 170-j or BLR0 175-0 is selected by YSWBj (j=0, 1, . . . , m−1) or YSWRB0, respectively. The Y-write pass gate 120-j (j=0, 1, . . . , m−1) or 125 can be built by PMOS, though NMOS, diode, or bipolar devices can be employed in some embodiments. Each BL or BLR0 is coupled to a dataline DL or DLR0 through a Y-read pass gate 130-j or 135 selected by YSRj (j=0, 1, . . . , m−1) or YSRR0, respectively. In this portion of memory array 101, m normal datalines DLj (j=0, 1, . . . , m−1) are connected to an input 160 of a sense amplifier 140. The reference dataline DLR0 provides another input 161 for the sense amplifier 140 (no multiplex is generally needed in the reference branch). The output of the sense amplifiers 140 is Q0.

To program a cell, the specific WLBi and YSWBj are turned on and a high voltage is supplied to VDDP, where i=0, 1, . . . n−1 and j=0, 1, . . . , m−1. In some embodiments, the reference cells can be programmed to 0 or 1 by turning on WLRBi, and YSWRB0, where i=0, 1, . . . , n−1. To read a cell, a data column 160 can be selected by turning on the specific WLBi and YSRj, where i=0, 1, . . . , n−1, and j=0, 1, . . . , m−1, and a reference cell coupled to the reference dataline DLR0 161 for the sense amplifier 140 can be selected to sense and compare the resistance difference between BLs and ground, while disabling all YSWBj and YSWRB0 where j=0, 1, . . . , m−1.

The programmable resistive devices can be used to construct a memory in accordance with one embodiment. FIG. 16( a) shows a portion of a programmable resistive memory 100 constructed by an array 101 of 3-terminal MRAM cells 110 in n rows and m+1 columns and n pairs of wordline drivers 150-i and 151-i, where i=0, 1, . . . , n−1, according to one embodiment. The memory array 101 has m normal columns and one reference column for one shared sense amplifier 140 for differential sensing. Each of the memory cells 110 has a resistive element 111 coupled to the P terminal of a program-0 diode 112 and N terminal of a program-1 diode 113. The program-0 diode 112 and the program-1 diode 113 serve as program selectors. Each resistive element 111 is also coupled to a bitline BLj 170-j (j=0, 1, . . . m−1) or reference bitline BLR0 175-0 for those of the memory cells 110 in the same column. The N terminal of the diode 112 is coupled to a wordline WLNi 152-i through a local wordline LWLNi 154-i, where i=0, 1, . . . , n−1, for those of the memory cells 110 in the same row. The P terminal of the diode 113 is coupled to a wordline WLPi 153-i through a local wordline LWLPi 155-i, where i=0, 1, . . . , n−1, for those cells in the same row. Each wordline WLNi or WLPi is coupled to at least one local wordline LWLNi or LWLPi, respectively, where i=0, 1, . . . , n−1. The LWLNi 154-i and LWLPi 155-i are generally constructed by a high resistivity material, such as N well or polysilicon, to connect cells, and then coupled to the WLNi or WLPi (e.g., low-resistivity metal WLNi or WLPi) through conductive contacts or vias, buffers, or post-decoders 172-i or 173-i respectively, where i=0, 1, . . . , n−1. Buffers or post-decoders 172-i or 173-i may be needed when using diodes as program selectors because there are currents flowing through WLNi or WLPi, especially when one WLNi or WLPi drivers multiple cells for program or read simultaneously in some embodiments. The wordlines WLNi and WLPi are driven by wordline drivers 150-i and 151-i, respectively, with a supply voltage vddi that can be switched between different voltages for program and read. Each BLj 170-j or BLR0 175-0 is coupled to a supply voltage VDDP through a Y-write-0 pass gate 120-0 or 125 to program 0, where each BLj 170-j or BLR0 175-0 is selected by YS0WBj (j=0, 1, . . . , m−1) or YS0WRB0, respectively. Y-write-0 pass gate 120-j or 125 can be built by PMOS, though NMOS, diode, or bipolar devices can be employed in other embodiments. Similarly, each BLj 170-j or BLR0 175-0 is coupled to a supply voltage 0V through a Y-write-1 pass gate 121-j or 126 to program 1, where each BLj 170-j or BLR0 175-0 is selected by YS1Wj (j=0, 1, . . . , m−1) or YS1WR0, respectively. Y-write-1 pass gate 121-j or 126 is can be built by NMOS, though PMOS, diode, or bipolar devices can be employed in other embodiments. Each BL or BLR0 is coupled to a dataline DL or DLR0 through a Y-read pass gate 130-j or 135 selected by YSRj (j=0, 1, . . . , m−1) or YSRR0, respectively. In this portion of memory array 101, m normal datalines DLj (j=0, 1, . . . , m−1) are connected to an input 160 of a sense amplifier 140. Reference dataline DLR0 provides another input 161 for the sense amplifier 140, except that no multiplex is generally needed in a reference branch. The output of the sense amplifier 140 is Q0.

To program a 0 into a cell, the specific WLNi, WLPi and BLj are selected as shown in FIG. 13( a) or 13(b) by wordline drivers 150-i, 151-i, and Y-pass gate 120-j by YS0WBj, respectively, where i=0, 1, . . . n−1 and j=0, 1, . . . , m−1, while the other wordlines and bitlines are also properly set. A high voltage is applied to VDDP. In some embodiments, the reference cells can be programmed into 0 by setting proper voltages to WLRNi 158-i, WLRPi 159-i and YS0WRB0, where i=0, 1, . . . , n−1. To program a 1 to a cell, the specific WLNi, WLPi and BLj are selected as shown in FIG. 12( a) or 12(b) by wordline driver 150-i, 151-i, and Y-pass gate 121-j by YS1 Wj, respectively, where i=0, 1, . . . n−1 and j=0, 1, . . . , m−1, while the other wordlines and bitlines are also properly set. In some embodiments, the reference cells can be programmed to 1 by setting proper voltages to WLRNi 158-i, WLRPi 159-i and YS1WR0, where i=0, 1, . . . , n−1. To read a cell, a data column 160 can be selected by turning on the specific WLNi, WLPi and YSRj, where i=0, 1, . . . , n−1, and j=0, 1, . . . , m−1, and a reference cell coupled to the reference dataline DLR 161 for the sense amplifier 140 to sense and compare the resistance difference between BLs and ground, while disabling all YS0WBj, YS0WRB0, YS1Wj and YS1WR0, where j=0, 1, . . . , m−1.

Another embodiment of constructing an MRAM memory with 2-terminal MRAM cells is shown in FIG. 16( b), provided the voltage difference VDDP, between high and low states, is less than twice of the diode's threshold voltage Vd, i.e., VDDP<2*Vd. As shown in FIG. 16( b), two wordlines per row WLNi 152-i and WLPi 153-i in FIG. 16( a) can be merged into one wordline driver WLNi 152-i, where i=0, 1, . . . , n−1. Also, the local wordlines LWLNi 154-i and LWLP 155-i per row in FIG. 16( a) can be merged into one local wordline LWLNi 154-i, where i=0, 1, . . . , n−1, as shown in FIG. 16( b). Still further, two wordline drivers 150-i and 151-i in FIG. 16( a) can be merged into one, i.e., wordline driver 150-i. The BLs and WLNs of the unselected cells are applied with proper program 1 and 0 conditions as shown in FIGS. 14( a) and 14(b), respectively. Since half of wordlines, local wordlines, and wordline drivers can be eliminated in this embodiment, cell and macro areas can be reduced substantially.

Differential sensing is a common for programmable resistive memory, though single-end sensing can be used in other embodiments. FIGS. 17( a), 17(b), and 17(c) show three other embodiments of constructing reference cells for differential sensing. In FIG. 17( a), a portion of memory 400 has a normal array 180 of n×m cells, two reference columns 150-0 and 150-1 of n×1 cells each storing all data 0 and 1 respectively, m+1 Y-read pass gates 130, and a sense amplifier 140. As an example, n=8 and m=8 are used to illustrate the concept. There are n wordlines WLBi and n reference wordlines WLRBi for each row, where i=0, 1, . . . , n−1. When a wordline WLBi is turned on to access a row, a corresponding reference wordline WLRBi (i=0, 1, . . . , n−1) is also turned on to activate two reference cells 170-0 and 170-1 in the same row to provide mid-level resistance after proper scaling in the sense amplifier. The selected dataline 160 along with the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, each WLRBi and WLBi (i=0, 1, . . . , n−1) are hardwired together and every cells in the reference columns need to be pre-programmed before read.

FIG. 17( b) shows another embodiment of using a reference cell external to a reference column. In FIG. 17( b), a portion of memory 400 has a normal array 180 of n×m cells, a reference column 150 of n×1 cells, m+1 Y-read pass gates 130, and a sense amplifier 140. When a wordline WLBi (i=0, 1, . . . , n−1) is turned on, none of the cells in the reference column 150 are turned on. An external reference cell 170 with a pre-determined resistance is turned on instead by an external reference wordline WLRB. The selected dataline 160 and the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, all internal reference wordlines WLRBi (i=0, 1, . . . , n−1) in each row are tied together to a high voltage to disable the diodes in the reference column. The reference column 150 provides a loading to match with that of the normal columns.

FIG. 17( c) shows another embodiment of constructing reference cells for differential sensing. In FIG. 17( c), a portion of memory 400 has a normal array 180 of n×m cells, one reference column 150 of n×1, two reference rows 175-0 and 175-1 of 1×m cells, m+1 Y-read pass gates 130, and a sense amplifier 140. As an example, n=8 and m=8 are used to illustrate the approach. There are n wordlines WLBi and 2 reference wordlines WLRB0 175-0 and WLRB1 175-1 on top and bottom of the array, where i=0, 1, . . . , n−1. When a wordline WLBi (i=0, 1, . . . , n−1) is turned on to access a row, the reference wordline WLRB0 and WLRB1 are also turned on to activate two reference cells 170-0 and 170-1 in the upper and lower right corners of the array 180, which store data 0 and 1 respectively. The selected dataline 160 along with the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, all cells in the reference column 150 are disabled except that the cells 170-0 and 170-1 on top and bottom of the reference column 150. Only two reference cells are used for the entire n×m array that needs to be pre-programmed before read.

For those programmable resistive devices that have a very small resistance ratio between states 1 and 0, such as 2:1 ratio in MRAM, FIGS. 17( a) and 17(c) are desirable embodiments, depending on how many cells are suitable for one pair of reference cells. Otherwise, FIG. 17( b) is a desirable embodiment for electrical fuse or PCM that has resistance ratio of more than about 10.

FIGS. 15, 16(a), 16(b), 17(a), 17(b), and 17(c) show only a few embodiments of a portion of programmable resistive memory in a simplified manner. The memory array 101 in FIGS. 15, 16(a), and 16(b) can be replicated s times to read or program s-cells at the same time. In the case of differential sensing, the number of reference columns to normal columns may vary and the physical location can also vary relative to the normal data columns. Rows and columns are interchangeable. The numbers of rows, columns, or cells likewise may vary. For those skilled in the art understand that the above descriptions are for illustrative purpose. Various embodiments of array structures, configurations, and circuits are possible and are still within the scope of this invention.

The portions of programmable resistive memories shown in FIGS. 15, 16(a), 16(b), 17(a), 17(b) and 17(c) can include different types of resistive elements. The resistive element can be an electrical fuse including a fuse fabricated from an interconnect, contact/via fuse, contact/via anti-fuse, or gate oxide breakdown anti-fuse. The interconnect fuse can be formed from silicide, metal, metal alloy, or some combination thereof, or can be constructed from a CMOS gate. The resistive element can also be fabricated from phase-change material, MTJ, etc. For the electrical fuse fabricated from an interconnect, contact, or via fuse, programming requirement is to provide a sufficiently high current, about 4-20 mA range, for a few microseconds to blow the fuse by electro-migration, heat, ion diffusion, or some combination thereof. For anti-fuse, programming requirement is to provide a sufficiently high voltage to breakdown the dielectrics between two ends of a contact, via or CMOS gate. The required voltage is about 6-7V for a few millisecond to consume about 10 uA of current in today's technologies. Programming Phase-Change Memory (PCM) requires different voltages and durations for 0 and 1. Programming to a 1 (or to reset) requires a high and short voltage pulse applied to the phase-change film. Alternatively, programming to a 0 (or to set) requires a low and long voltage pulse applied to the phase change film. The reset needs about 3V for 50 ns and consumes about 300 uA, while set needs about 2V for 300 ns and consumes about 100 uA. For MRAM, the high and low program voltages are about 2-3V and 0V, respectively, and the current is about +/−100-200 uA.

Most programmable resistive devices have a higher voltage VDDP (˜2-3V) for programming than the core logic supply voltage VDD (˜1.0V) for reading. FIG. 18( a) shows a schematic of a wordline driver circuit 60 according to one embodiment. The wordline driver includes devices 62 and 61, as shown as the wordline driver 150 in FIGS. 15, 16(a) and 16(b). The supply voltage vddi is further coupled to either VDDP or VDD through power selectors 63 and 64 (e.g., PMOS power selectors) respectively. The input of the wordline driver Vin is from an output of an X-decoder. In some embodiments, the power selectors 63 and 64 are implemented as thick oxide I/O devices to sustain high voltage. The bodies of power selector 63 and 64 can be tied to vddi to prevent latchup.

Similarly, bitlines tend to have a higher voltage VDDP (˜2-3V) for programming than the core logic supply voltage VDD (˜1.0V) for reading. FIG. 18( b) shows a schematic of a bitline circuit 70 according to one embodiment. The bitline circuit 70 includes a bitline (BL) coupled to VDDP and VDD through power selectors 73 and 74 (e.g., PMOS power selectors), respectively. If the bitline needs to sink a current such as in an MRAM, an NMOS pulldown device 71 can be provided. In some embodiments, the power selectors 73 and 74 as well as the pulldown device 71 can be implemented as thick-oxide I/O devices to sustain high voltage. The bodies of power selector 73 and 74 can be tied to vddi to prevent latchup.

Using junction diodes as program selectors may have high leakage current if a memory size is very large. Power selectors for a memory can help reducing leakage current by switching to a lower supply voltage or even turning off when a portion of memory is not in use. FIG. 18( c) shows a portion of memory 85 with an internal power supply VDDP coupled to an external supply VDDPP and a core logic supply VDD through power selectors 83 and 84. VDDP can even be coupled to ground by an NMOS pulldown device 81 to disable this portion of memory 85, if this portion of memory is temporarily not in use.

FIGS. 19( a) and 20(a) only show two of many pre-amplifier embodiments. Similarly, FIGS. 19( b), 20(b) and 20(c) only show several of many amplifier and level shifter embodiments. Various combinations of pre-amplifiers, level shifters, and amplifiers in core logic or I/O devices can be constructed differently, separately or mixed.

FIG. 19( a) shows one embodiment of a schematic of a pre-amplifier 100 according to one embodiment. The pre-amplifier 100 needs special considerations because the supply voltage VDD for core logic devices is about 1.0V that does not have enough head room to turn on a diode to make sense amplifiers functional, considering a diode's threshold is about 0.7V. One embodiment is to use another supply VDDR, higher than VDD, to power at least the first stage of sense amplifiers. The programmable resistive cell 110 shown in FIG. 19( a) has a resistive element 111 and a diode 112 as program selector, and can be selected for read by asserting YSR′ to turn on a gate of a NMOS 130 (NMOS device) and wordline bar WLB. The pre-amplifier 100 also has a reference cell 115 including a reference resistive element 116 and a reference diode 117. The reference cell 115 can be selected for differential sensing by asserting YSR′ to turn on a gate of a NMOS 131 and reference wordline WLRB. The resistance Ref of the reference resistive element 116 can be set at a resistance half-way between minimum of state 1 and maximum of state 0 resistance.

The drains of NMOS 130 and 131 are coupled to sources of NMOS 132 and 134, respectively. The gates of 132 and 134 are biased at a fixed voltage Vbias. The channel width to length ratios of NMOS 132 and 134 can be relatively large to clamp the voltage swings of bitline BL and reference bitline BLR, respectively. The drain of NMOS 132 and 134 are coupled to drains of PMOS 170 and 171, respectively. The drain of PMOS 170 is coupled to the gate of PMOS 171 and the drain of PMOS 171 is coupled to the gate of PMOS 170. The outputs V+ and V− of the pre-amplifier 100 are drains of PMOS 170 and PMOS 171 respectively. The sources of PMOS 170 and PMOS 171 are coupled to a read supply voltage VDDR. The outputs V+ and V− are pulled up by a pair of PMOS 175 to VDDR when the pre-amplifier 100 is disabled. VDDR is about 2-3V (which is higher than about 1.0V VDD of core logic devices) to turn on the diode selectors 112 and 117 in the programmable resistive cell 110 and the reference cell 115, respectively. The CMOS 130, 131, 132, 134, 170, 171, and 175 can be embodied as thick-oxide I/O devices to sustain high voltage VDDR. In another embodiment, the read selectors 130 and 131 can be PMOS devices.

FIG. 19( b) shows one embodiment of a schematic of an amplifier 200 according to one embodiment. In another embodiment, the outputs V+ and V− of the pre-amplifier 100 in FIG. 19( a) can be coupled to gates of NMOS 234 and 232, respectively, of the amplifier 200. The NMOS 234 and 232 can be relatively thick oxide I/O devices to sustain the high input voltage V+ and V− from a pre-amplifier. The sources of NMOS 234 and 232 are coupled to drains of NMOS 231 and 230, respectively. The sources of NMOS 231 and 230 are coupled to a drain of an NMOS 211. The gate of NMOS 211 is coupled to a clock φ to turn on the amplifier 200, while the source of NMOS 211 is coupled to ground. The drains of NMOS 234 and 232 are coupled to drains of PMOS 271 and 270, respectively. The sources of PMOS 271 and 270 are coupled to a core logic supply VDD. The gates of PMOS 271 and NMOS 231 are connected and coupled to the drain of PMOS 270, as a node Vp. Similarly, the gates of PMOS 270 and NMOS 230 are connected and coupled to the drain of PMOS 271, as a node Vn. The nodes Vp and Vn are pulled up by a pair of PMOS 275 to VDD when the amplifier 200 is disabled when φ goes low. The output nodes Vout+ and Vout− are coupled to nodes Vn and Vp through a pair of inverters as buffers.

FIG. 19( c) shows a timing diagram of the pre-amplifier 100 and the amplifier 200 in FIGS. 19( a) and 19(b), respectively. The X- and Y-addresses AX/AY are selected to read a cell. After some propagation delays, a cell is selected for read by turning WLB low and YSR high to thereby select a row and a column, respectively. Before activating the pre-amplifier 100, a pulse Vpc is generated to precharge DL and DLR to ground. The pre-amplifier 100 would be very slow if the DL and DLR voltages are high enough to turn off the cascode devices (e.g., NMOS 132 and 134). After the pre-amplifier outputs V+ and V− are stabilized, the clock φ is set high to turn on the amplifier 200 and to amplify the final output Vout+ and Vout− into full logic levels.

FIG. 20( a) shows another embodiment of a pre-amplifier 100′, similar to the pre-amplifier 100 in FIG. 18( a). The reference branch is turned on by a level signal to enable a sense amplifier, SAEN, rather than cycle by cycle in FIG. 19( a). The PMOS pull-ups 171 and 170 in FIG. 20( a) are configured as current mirror loads, rather than a pair of cross-coupled PMOS in FIG. 19( a). In this embodiment, the number of the reference branches can be shared at the expense of increasing power consumption.

FIG. 20( b) shows level shifters 300 according to one embodiment. The V+ and V− from the pre-amplifier 100, 100′ outputs in FIG. 19( a) or FIG. 20( a) are coupled to gates of NMOS 301 and 302, respectively. The drains of NMOS 301 and 302 are coupled to a supply voltage VDDR. The sources of NMOS 301 and 302 are coupled to drains of NMOS 303 and 304, respectively, which have gates and drains connected as diodes to shift the voltage level down by one Vtn, the threshold voltage of an NMOS. The sources of NMOS 303 and 304 are coupled to pulldown devices NMOS 305 and 306, respectively. The gates of NMOS 305 and 306 can be turned on by a clock φ. The NMOS 301, 302, 303 and 304 can be thick-oxide I/O devices to sustain high voltage VDDR. The NMOS 303 and 304 can be cascaded more than once to shift V+ and V− further to proper voltage levels Vp and Vn. In another embodiment, the level shifting devices 303 and 304 can be built using PMOS devices.

FIG. 20( c) shows another embodiment of an amplifier 200′ with current-mirror loads having PMOS 270 and 271. The inputs Vp and Vn of the amplifier 200′ are from the outputs Vp and Vn of the level shifter 300 in FIG. 20( b) can be coupled to gates of NMOS 231 and 230, respectively. The drains of NMOS 231 and 230 are coupled to drains of NMOS 271 and 270 which provide current-mirror loads. The drain and gate of PMOS 271 are connected and coupled to the gate of PMOS 270. The sources of NMOS 231 and 230 are coupled to the drain of an NMOS 211, which has the gate coupled to a clock signal φ and the source to ground. The clock signal φ enables the amplifier 200. The drain of PMOS 270 provides an output Vout+. The PMOS pullup 275 keeps the output Vout+ at logic high level when the amplifier 200′ is disabled.

FIGS. 21( a) and 21(b) show a flow chart depicting embodiments of a program method 700 and a read method 800, respectively, for a programmable resistive memory in accordance with certain embodiments. The methods 700 and 800 are described in the context a programmable resistive memory, such as the programmable resistive memory 100 in FIGS. 15, 16(a) and 16(c). In addition, although described as a flow of steps, one of ordinary skilled in the art will recognize that at least some of the steps may be performed in a different order, including simultaneously, or skipped.

FIG. 21( a) depicts a method 700 of programming a programmable resistive memory in a flow chart according to one embodiment. In the first step 710, proper power selectors can be selected so that high voltages can be applied to the power supplies of wordline drivers and bitlines. In the second step 720, the data to be programmed in a control logic (not shown in FIGS. 15, 16(a), and 16(b)) can be analyzed, depending on what types of programmable resistive devices. For electrical fuse, this is a One-Time-Programmable (OTP) device such that programming always means blowing fuses into a non-virgin state and is irreversible. Program voltage and duration tend to be determined by external control signals, rather than generated internally from the memory. For PCM, programming into a 1 (to reset) and programming into a 0 (to set) require different voltages and durations such that a control logic determines the input data and select proper power selectors and assert control signals with proper timings. For MRAM, the directions of current flowing through MTJs are more important than time duration. A control logic determines proper power selectors for wordlines and bitlines and assert control signals to ensure a current flowing in the desired direction for desired time. In the third step 730, a cell in a row can be selected and the corresponding local wordline can be turned on. In the fourth step 740, sense amplifiers can be disabled to save power and prevent interference with the program operations. In the fifth step 750, a cell in a column can be selected and the corresponding Y-write pass gate can be turned on to couple the selected bitline to a supply voltage. In the last step 760, a desired current can be driven for a desired time in an established conduction path to complete the program operations. For most programmable resistive memories, this conduction path is from a high voltage supply through a bitline select, resistive element, diode as program selector, and an NMOS pulldown of a local wordline driver to ground. Particularly, for programming a 1 to an MRAM, the conduction path is from a high voltage supply through a PMOS pullup of a local wordline driver, diode as program selector, resistive element, and bitline select to ground.

FIG. 21( b) depicts a method 800 of reading a programmable resistive memory in a flow chart according to one embodiment. In the first step 810, proper power selectors can be selected to provide supply voltages for local wordline drivers, sense amplifiers, and other circuits. In the second step 820, all Y-write pass gates, i.e. bitline program selectors, can be disabled. In the third step 830, desired local wordline(s) can be selected so that the diode(s) as program selector(s) have a conduction path to ground. In the fourth step 840, sense amplifiers can be enabled and prepared for sensing incoming signals. In the fifth step 850, the dataline and the reference dataline can be pre-charged to the V− voltage of the programmable resistive device cell. In the sixth step 860, the desired Y-read pass gate can be selected so that the desired bitline is coupled to an input of the sense amplifier. A conduction path is thus established from the bitline to the resistive element in the desired cell, diode(s) as program selector(s), and the pulldown of the local wordline driver(s) to ground. The same applies for the reference branch. In the last step 870, the sense amplifiers can compare the read current with the reference current to determine a logic output of 0 or 1 to complete the read operations.

FIG. 22 shows a processor system 700 according to one embodiment. The processor system 700 can include a programmable resistive device 744, such as in a cell array 742, in memory 740, according to one embodiment. The processor system 700 can, for example, pertain to a computer system. The computer system can include a Central Process Unit (CPU) 710, which communicate through a common bus 715 to various memory and peripheral devices such as I/O 720, hard disk drive 730, CDROM 750, memory 740, and other memory 760. Other memory 760 is a conventional memory such as SRAM, DRAM, or flash, typically interfaces to CPU 710 through a memory controller. CPU 710 generally is a microprocessor, a digital signal processor, or other programmable digital logic devices. Memory 740 is preferably constructed as an integrated circuit, which includes the memory array 742 having at least one programmable resistive device 744. The memory 740 typically interfaces to CPU 710 through a memory controller. If desired, the memory 740 may be combined with the processor, for example CPU 710, in a single integrated circuit.

The invention can be implemented in a part or all of an integrated circuit in a Printed Circuit Board (PCB), or in a system. The programmable resistive device can be fuse, anti-fuse, or emerging nonvolatile memory. The fuse can be silicided or non-silicided polysilicon fuse, metal fuse, contact fuse, or via fuse. The anti-fuse can be a gate-oxide breakdown anti-fuse, contact or via anti-fuse with dielectrics in-between. The emerging nonvolatile memory can be Magnetic RAM (MRAM), Phase Change Memory (PCM), Conductive Bridge RAM (CBRAM), or Resistive RAM (RRAM). Though the program mechanisms are different, their logic states can be distinguished by different resistance values.

The above description and drawings are only to be considered illustrative of exemplary embodiments, which achieve the features and advantages of the present invention. Modifications and substitutions of specific process conditions and structures can be made without departing from the spirit and scope of the present invention.

The many features and advantages of the present invention are apparent from the written description and, thus, it is intended by the appended claims to cover all such features and advantages of the invention. Further, since numerous modifications and changes will readily occur to those skilled in the art, it is not desired to limit the invention to the exact construction and operation as illustrated and described. Hence, all suitable modifications and equivalents may be resorted to as falling within the scope of the invention. 

What is claimed is:
 1. A reversible resistive memory, comprising: a plurality of reversible resistive cells, at least one of the reversible resistive cells comprising: a plurality of active region lines running in a first direction, each of the active region lines being in separated by a CMOS well; a plurality of isolation lines running in a second direction substantially perpendicular to the first direction to separate one or more of the active region lines into a plurality of isolated active regions, at least one of the isolated active regions being fabricated from sources or drains of CMOS devices and being implanted with a first type of dopant and a shared second type of dopant to constitute a first and a second terminals of diodes, respectively, the second terminal of the diodes being coupled to a first supply voltage line; a plurality of metal lines running in the second direction and coupled to a second supply voltage line; a contact hole being built at a cross over point of the metal lines and the isolated active regions; and at least one reversible resistive element built in the contact hole that couples to the isolated active region with the first type of dopant and to the metal lines, wherein the reversible resistive film is configured to be programmable by applying voltages to the first and the second supply voltage lines to change the resistance into a different logic state in a reversible manner.
 2. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film comprises a phase-change film in a phase-change RAM (PCRAM), resistive film in a resistive RAM (RRAM), or a film in a conductive bridge RAM (CBRAM).
 3. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film comprises a phase-change film that has chemical composition of Germanium (Ge), Antimony (Sb), and Tellurium (Te).
 4. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film comprises a metal oxide film between metal or metal alloy electrodes.
 5. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film comprises a solid-state electrolyte film between metal or metal alloy electrodes.
 6. A reversible resistive memory as recited in claim 1, wherein the ratio of the isolated active regions with the first type of dopant to the second type of dopant is equal or larger than
 8. 7. A reversible resistive memory as recited in claim 1, wherein the at least one of the CMOS wells to house the isolated active regions is the same CMOS well to house MOS devices.
 8. A reversible resistive memory as recited in claim 1, wherein the CMOS wells that house the isolated active regions are the shallower than the CMOS wells to house MOS devices.
 9. A reversible resistive memory as recited in claim 1, wherein at least one of the isolation lines separates one or more of the active region lines into isolated active regions, and is implemented using shallow trench isolation used for isolating CMOS devices.
 10. A reversible resistive memory as recited in claim 1, wherein at least one of the isolation lines separates one or more of the active region lines into isolated active regions, and is implemented using a dummy CMOS gate.
 11. A reversible resistive memory as recited in claim 1, wherein at least one of the isolation lines separates one or more of the active region lines into isolated active regions, and is implemented using a silicide block layer.
 12. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film is configured to be programmed by a high voltage and/or short duration to one state and a low voltage and/or long duration to another.
 13. A reversible resistive memory as recited in claim 1, wherein the reversible resistive film is configured to be programmed by using a current limit or a voltage limit.
 14. An electronic system, comprising: a processor; and a reversible resistive memory operatively connected to the processor, the reversible resistive memory comprises a plurality of reversible resistive cells, at least one of the reversible resistive cells including at least: a plurality of active region lines running in a first direction, each of the active region lines being in separated by a CMOS well; a plurality of isolation lines running in a second direction substantially perpendicular to the first direction to separate one or more of the active region lines into a plurality of isolated active regions, at least one of the isolated active regions being fabricated from sources or drains of CMOS devices and being implanted with a first type of dopant and a shared second type of dopant to constitute a first and a second terminals of diodes, respectively, the second terminal of the diodes being coupled to a first supply voltage line; a plurality of metal lines running in the second direction and coupled to a second supply voltage line; a contact hole being built at a cross over point of the metal lines and the isolated active regions; and at least one reversible resistive element built in the contact hole that couples to the isolated active region with the first type of dopant and to the metal lines, wherein the reversible resistive film is configured to be programmable by applying voltages to the first and the second supply voltage lines to change the resistance into a different logic state in a reversible manner.
 15. An electronic system as recited in claim 14, wherein the reversible resistive film comprises a phase-change film in a phase-change RAM (PCRAM), resistive film in a resistive RAM (RRAM), or a film in a conductive bridge RAM (CBRAM).
 16. A reversible resistive memory as recited in claim 14, wherein the CMOS wells that house the isolated active regions are the shallower than the CMOS wells to house MOS devices.
 17. A reversible resistive memory as recited in claim 14, wherein at least one of the isolation lines separates one or more of the active region lines into isolated active regions, and is implemented using a dummy CMOS gate.
 18. An electronic system as recited in claim 14, wherein the reversible resistive film comprises a metal oxide film between metal or metal alloy electrodes.
 19. An electronic system as recited in claim 14, wherein the reversible resistive film comprises a solid-state electrolyte film between metal or metal alloy electrodes.
 20. An electronic system as recited in claim 14, wherein the reversible resistive film is configured to be programmed by a high voltage and/or short duration to one state and a low voltage and/or long duration to another.
 21. An electronic system as recited in claim 14, wherein the reversible resistive film is configured to be programmed by using a current limit or a voltage limit. 